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PDF ( 数据手册 , 数据表 ) OP-184

零件编号 OP-184
描述 Precision Rail-to-Rail Input & Output Operational Amplifiers
制造商 Analog Devices
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OP-184 数据手册, 描述, 功能
a
FEATURES
Single-Supply Operation
Wide Bandwidth: 4 MHz
Low Offset Voltage: 65 V
Unity-Gain Stable
High Slew Rate: 4.0 V/s
Low Noise: 3.9 nV/Hz
APPLICATIONS
Battery Powered Instrumentation
Power Supply Control and Protection
Telecom
DAC Output Amplifier
ADC Input Buffer
Precision Rail-to-Rail Input & Output
Operational Amplifiers
OP184/OP284/OP484
PIN CONFIGURATIONS
8-Lead Epoxy DIP
(P Suffix)
8-Lead SO
(S Suffix)
NULL 1
–IN A 2
+IN A 3
V– 4
OP184
8 NC
7 V+
6 OUT A
5 NULL
NC = NO CONNECT
GENERAL DESCRIPTION
The OP184/OP284/OP484 are single, dual and quad single-
supply, 4 MHz bandwidth amplifiers featuring rail-to-rail inputs
and outputs. They are guaranteed to operate from +3 to +36 (or
± 1.5 to ± 18) volts and will function with a single supply as low
as +1.5 volts.
These amplifiers are superb for single supply applications re-
quiring both ac and precision dc performance. The combination
of bandwidth, low noise and precision makes the OP184/OP284/
OP484 useful in a wide variety of applications, including filters
and instrumentation.
Other applications for these amplifiers include portable telecom
equipment, power supply control and protection, and as amplifi-
ers or buffers for transducers with wide output ranges. Sensors
requiring a rail-to-rail input amplifier include Hall effect, piezo
electric, and resistive transducers.
The ability to swing rail-to-rail at both the input and output en-
ables designers to build multistage filters in single-supply sys-
tems and to maintain high signal-to-noise ratios.
The OP184/OP284/OP484 are specified over the HOT extended
industrial (–40°C to +125°C) temperature range. The single
and dual are available in 8-pin plastic DIP plus SO surface
mount packages. The quad OP484 is available in 14-pin plastic
DIPs and 14-lead narrow-body SO packages.
8-Lead Epoxy DIP
(P Suffix)
8-Lead SO
(S Suffix)
OUT A 1
–IN A 2
+IN A 3
V– 4
OP284 8 V+
7 OUT B
6 –IN B
5 +IN B
14-Lead Epoxy DIP
(P Suffix)
14-Lead Narrow-Body SO
(S Suffix)
OUT A 1
–IN A 2
+IN A 3
V+ 4
+IN B 5
–IN B 6
OUT B 7
OP484
14 OUT D
13 –IN D
12 +IN D
11 V–
10 +IN C
9 –IN C
8 OUT C
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700 World Wide Web Site: http://www.analog.com
Fax: 617/326-8703
© Analog Devices, Inc., 1996







OP-184 pdf, 数据表
OP184/OP284/OP484–Typical Performance Characteristics
300
270 VS = +5V
TA = +25°C
240
AV = 10
210
180 AV = 100
150
120
90
60
30
0
100
AV = 1
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 20. Output Impedance vs.
Frequency
5
4
3
2
VS = +5V
VIN = 0.5–4.5V
1 RL = 2k
TA = +25°C
0
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 23. Maximum Output Swing
vs. Frequency
160
140 TA = +25°C
120
100
80
60 VS = ±15V
40
VS = +5V
20
0
–20 VS = +3V
–40
100
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 26. PSRR vs. Frequency
300
270 VS = ±15V
TA = +25°C
240
210
180
AV = 100
AV = 10
150
120
90
60
30
0
100
AV = 1
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 21. Output Impedance vs.
Frequency
30
VS = ±15V
25 VIN = ±14V
RL = 2k
TA = +25°C
20
15
10
5
0
1k 10k 100k 1M 10M
FREQUENCY – Hz
Figure 24. Maximum Output Swing
vs. Frequency
80
70 VS = ±2.5V
TA = +25°C, AVCL = 1
60 VIN = ±50mV
–OS
50
40
+OS
30
20
10
0
10 100
CAPACITIVE LOAD – pF
1000
Figure 27. Small Signal Overshoot
vs. Capacitive Load
300
270 VS = +3V
TA = +25°C
240
AV = 100
210
180
150
120
90
60
30
0
100
AV = 10
AV = 1
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 22. Output Impedance vs.
Frequency
180
160 TA = +25°C
140
120
100
80 VS = ±15V
60
40 VS = +3V
20 VS = +5V
0
–20
100
1k 10k 100k 1M
FREQUENCY – Hz
10M
Figure 25. CMRR vs. Frequency
7
6
+SLEW RATE
5
–SLEW RATE
4
VS = ±15V
RL = 2k
3 +SLEW RATE
2 –SLEW RATE
1
0
–50 –25
VS = +5V
RL = 2k
0 25 50 75 100 125
TEMPERATURE – °C
Figure 28. Slew Rate vs. Temperature
–8– REV. 0







OP-184 equivalent, schematic
OP184/OP284/OP484
Obviously, it is desirable to keep this comparison voltage small,
since it becomes a significant portion of the overall dropout
voltage. Here, the 20 mV reference is higher than the typical
offset of the OP284 but still reasonably low as a percentage of
VOUT (< 0.5%). In adapting the limiter for other ILIMIT levels,
sense resistor RS should be adjusted along with R7-R8, to main-
tain this threshold voltage between 20 mV and 50 mV.
Performance of the circuit is excellent. For the 4.5 V output
version, the measured dc output change for a 225 mA load
change was on the order of a few microvolts while the dropout
voltage at this same current level was about 30 mV. The current
limit as shown is 400 mA, which allows the circuit to be used at
levels up to 300 mA or more. While the Q1 device can actually
support currents of several amperes, a practical current rating
takes into account the SO-8 device’s 2.5 W, 25°C dissipation.
Because a short circuit current of 400 mA at an input level of 5
V will cause a 2 W dissipation in Q1, other input conditions
should be considered carefully in terms of Q1’s potential over-
heating. Of course, if higher powered devices are used for Q1,
this circuit can support outputs of tens of amperes as well as the
higher VOUT levels noted above.
The circuit shown can be used either as a standard low dropout
regulator, or it can be used with ON/OFF control. By
driving Pin 3 of U1 with the optional logic control signal VC, the
output is switched between ON and OFF. Note that when the
output is OFF in this circuit, it is still active (i.e., not an open cir-
cuit). This is because the OFF state simply reduces the voltage
input to R1, leaving the U1A/B amplifiers and Q1 still active.
When ON/OFF control is used, resistor R10 should be used
with U1 to speed ON-OFF switching and to allow the output of
the circuit to settle to a nominal zero voltage. Components D3
and R11 also aid in speeding up the ON-OFF transition by pro-
viding a dynamic discharge path for C2. OFF-ON transition
time is less than 1 ms, while the ON-OFF transition is longer
but under 10 ms.
A +3 V, 50 Hz/60 Hz Active Notch Filter with False Ground
To process signals in a single-supply system, it is often best
to use a false ground biasing scheme. A circuit that uses this
approach is illustrated in Figure 56. In this circuit, a false-ground
circuit biases an active notch filter used to reject 50 Hz/60 Hz
power line interference in portable patient monitoring equip-
ment. Notch filters are quite commonly used to reject power
line frequency interference that often obscures low frequency
physiological signals, such as heart rates, blood pressure read-
ings, EEGs, EKGs, etc. This notch filter effectively squelches
60 Hz pickup at a filter Q of 0.75. Substituting 3.16 kresis-
tors for the 2.67 kin the twin-T section (R1 through R5)
configures the active filter to reject 50 Hz interference.
R2
2.67k
+3V
R1
2.67k
C1
24
1µF
C2
1µF
A1 1
VIN 3 11
R3
2.67k
R4
2.67k
5
A2
6
7
R6
10k
C3
2µF
(1µF x 2)
R5
1.33k
(2.67kΩ ÷ 2)
R8
1k
R7
1k
VO
R11
10k
C5 Q = 0.75
0.03µF
+3V
NOTE: FOR 50Hz APPLICATIONS
CHANGE R1–R4 TO 3.1k
R9 9
R12
150
AND R5 TO 1.58k(3.16kΩ ÷ 2).
20k
A3 8
10 1.5V
C6
C4 R10
1µF
1µF
20k
A1, A2, A3 = OP484
Figure 56. A +3 V Single Supply, 50/60 Hz Active Notch
Filter with False Ground
Amplifier A3 is the heart of the false-ground bias circuit. It
simply buffers the voltage developed at R9 and R10 and is the
reference for the active notch filter. Since the OP484 exhibits a
rail-to-rail input common-mode range, R9 and R10 are chosen
to split the +3 V supply symmetrically. An in-the-loop compen-
sation scheme is used around the OP484 that allows the op amp
to drive C6, a 1 µF capacitor, without oscillation. C6 maintains
a low impedance ac ground over the operating frequency range
of the filter.
The filter section uses a OP484 in a twin-T configuration whose
frequency selectivity is very sensitive to the relative matching of
the capacitors and resistors in the twin-T section. Mylar is the
material of choice for the capacitors, and the relative matching
of the capacitors and resistors determines the filter’s pass band
symmetry. Using 1% resistors and 5% capacitors produces
satisfactory results.
–16–
REV. 0










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